Supplementary Material
to:
An Introduction to Radio Astronomy
4th edition Cambridge University Press 2019
Last updated 1/07/2019
Chapter 6: Radiometers
Schematic illustration of the action
of a mixer
The essence
of mixing is captured by the action of an “on-off” switch in which the
conductance of a diode is controlled by the varying local oscillator (LO)
voltage VLO.
In the top panel the varying
input LO and radio frequency (RF) and output intermediate frequency (IF)
voltages are represented by square waves for simplicity. In the bottom panel
the output spectrum of the intermediate frequency (IF) signal is shown.
Notes:
-
In practice VLO >> VRF;
ii) the LO frequency fLO
is shown as higher than the RF frequency fRF
but this is an arbitrary choice.
-
When the LO voltage (period 4 units say equivalent to fLO = “250 MHz”) is positive (red) the switch passes
the RF signal (period 6 units equivalent to fRF
=“166.67 MHz”). When the LO voltage is negative (blue) the RF signal is not
passed.
-
The IF signal can be seen to have a component with
a repetition period of 12 units equivalent to fIF
= “83.33 MHz” i.e. the difference frequency.
As can be seen, however,
there are other frequency components in the IF signal and in practice a wide range
of harmonics, and mixtures between them can be generated; this is shown
schematically in an output spectrum in the bottom panel. The
desired frequency component has to be selected out by a filter and the power in
it is always significantly less that in the original RF signal; this is called
the “conversion loss” and is typically in the range 6-10dB (see section 6.6).
Receiver Temperature
Calibration
Measuring Trec with a microwave absorber (IRA4 Section 6.5).The telescope aperture is covered with absorbing material (right) at ambient temperature, measuring the contrast between the (cold) sky temperature and the ambient temperature of the absorber.
In order to determine the receiver temperature output power measurements are taken for at least two sources of known input power. A sheet of carbon-loaded microwave absorber (top) radiates very like a black-body over a particular frequency range and is often used as the “hot load” at ambient temperature. A “cold load” can be created by soaking the absorber in liquid nitrogen (LN2) at a temperature of 77K. Here we show the absorber as a hot load being held over the mouth of an experimental corrugated test horn which is connected to a receiver. For the most accurate work the characteristics of the absorber must be precisely known at the observing frequency (from the manufacturer’s specification plus lab. bench measurements); the back of the absorber should be covered with reflecting material (a metal sheet) to double its effective depth. The temperature of the hot load must be measured at representative places and the known effect of atmospheric pressure on the boiling point of LN2 should be taken into account for the cold load. To achieve a lower temperature cold load liquid helium is used but the costs are much higher than for LN2.
For state-of-the-art discussions about precision total power
calibration see:
C. Tello, T. Villela, S. Torres, M. Bersanelli,
G. F. Smoot, I. S. Ferreira, A. Cingoz, J. Lamb, D.
Barbosa, D. Perez-Becker, S. Ricciardi, J. A. Currivan, P. Platania,
and D.Maino, “The 2.3 GHz survey of the GEM project”,
A&A, 516, A1 (2013)
Singal,
J; Fixsen, D.J; Kogut, A;
Levin, S; Limon,
M; Lubin, P ; Mirel, P; Seiffert, M; Villela, T; Wollack, E; Wuensche, C.A; 2011
“The ARCADE” Instrument”, ApJ, 730:138.
The universality of “1/f noise”
The appearance of 1/f spectra in a wide variety of natural phenomena has been discussed by, among others,
Milotti, E. (2002) https://arxiv.org/ftp/physics/papers/0204/0204033.pdf
Ward, L.M. and Greenwood, P.E. (2007) http://www.scholarpedia.org/article/1/f_noise
Schematic signal flow in a Dicke-switch system.
Schematic signal flow in a Dicke-switch system.
In this receiver system (see Section 6.8.1) the noise power from an
antenna is compared with that from a resistive load. The illustration shows the flow of signal
through the system.
If the
receiver gain fluctuations DG(t) were very slow (e.g. minutes) then one could calibrate a radiometer
by frequently pointing the antenna at a sky reference region of known
brightness. In practice the gain
fluctuations (“1/f noise”) are much too fast for this approach and so in the Dicke switch system the comparison power source is built
into the receiver itself in the form of a resistive load; the receiver input is
switched between the antenna and the load (main text Fig 6.13). In the upper
part of the signal flow diagram schematic output power fluctuations are shown
for the case when TA>Tload.
The relative gain variations DG(t)/G
have been greatly exaggerated by suppressing the
steady (P0) part of POUT (t); they are typically 1:10-4 to 1:10-5. If tswitch<< 1/fknee
the gain variations over a switching cycle will be small –akin to a fast
shutter speed on a camera freezing the motion of a target. Note,
however, that for ease of drawing tswitch
is here only somewhat smaller than 1/fknee
rather than very much smaller. The lower portion of the signal flow
diagram shows the power output for the two states Pout a (Trec+Tload) and Pout a (Trec+TA) over a few switch cycles. The
synchronous detector system responds to the average power difference a<Tload-TA> rather than to the unswitched power a<Trec+TA> and thus the relative improvement in stability on the timescale
of tswitch is [Trec+ TA]/ [Tload -TA].
State-of-the-art Dicke-switch
applications:
The advantages and
disadvantages of Dicke switch receivers are described
in the main text. They are used in accurate radiometers to measure atmospheric
water vapour e.g. Tanner E.W. Radio
Science, 33,449 (1998). Current
high-profile applications are the 183 GHz water vapour radiometers for ALMA
(Section 11.3) and the Earth resources satellites Aquarius (https://aquarius.nasa.gov ) and SMAP (https://smap.jpl.nasa.gov/mission/description/) which both use L-band radiometry demanding
great precision and stability.
An example of a twin-beam radiometer: the
30 GHz OCRA-p system
As explained
in section 8.6.1 and Supplementary Material Chapter 8, a twin-beam receiver,
which continuously takes the difference between the power in closely-spaced
beams, greatly reduces the effect of tropospheric fluctuations, ground spillover and receiver gain changes. An example of such a system is the 30 GHz (λ
= 1cm) OCRA-p radiometer (Lowe 2016 ; Lowe et al 2007) mounted on the 32m dish of
the Torun Centre for Astronomy. In the
drawing (left) the two corrugated horns (inner diameter at mouth = 80mm) feed
power to a correlation receiver whose architecture is similar to that of the Planck
LFI radiometers (see below and Chapter 17). The components (including the horns) above the
horizontal plate are in a cryostat cooled to ~20K; below the plate the
components are at ambient temperature. In the photograph (right) the receiver is
shown prior to mounting on the telescope.
The white material at the top is to prevent condensation forming on the
microwave-transparent window (above the horns and not visible) which separates
the atmosphere from the vacuum inside the cryostat. The red pipe feeds dry nitrogen into the
space between the white material and the window to further reduce condensation
on the window. (Drawing credit S. Lowe)
References
·
Lowe, S.R. PhD Thesis, University of
Manchester (2016)
·
Lowe, S. R., Gawronski, M. P.,
Wilkinson, P. N., Kus, A. J., Browne, I. W. A., Pazderski, E., Feiler, R., and Kettle, D. 2007. 30 GHz flux
density measurements of the Caltech-Jodrell flat-spectrum sources with OCRA-p.
A&A, 474(Nov.), 1093–1100.
Schematic of a basic correlation
receiver
Power from two closely-spaced beams (red
and blue directions) enter the receiver and are continuously compared. The
voltage outputs VA1 and VA2 (alternatively the comparison
could be a temperature controlled load Vload) have, by means of the hybrid splitters, passed through both receivers and
hence are subject to the same gain
fluctuations. After square law detection the
powers (TA1 and TA2 or Tload) therefore vary together and
the difference TA1 - TA2 goes to zero if the receiver
inputs are exactly balanced. When there
is different emission in one of the beams (near field atmosphere or far field
sources), this will appear
in the difference signal. This is
the essence of the OCRA-p architecture. In practice additional amplification is
required after the second hybrid splitters and before power detection. Since
the gain of these amplifiers will also vary an additional time modulation is
applied in one arm between the splitters by means of 180o phase
switch. In a manner reminiscent of the operation of a DIcke
switch system by subtracting the modulated signals the effect of the gain
variations can be greatly reduced. This
is shown in the schematic OCRA-p and Planck LFI radiometers below.
A
schematic of the OCRA-p correlation receiver showing the phase switches between
the two hybrid splitters. Only one of
the phase switches is actually driven the other is in place to balance the
characteristics of the two arms. The phase shifters allow small changes to the
path length of the signal in the two arms to be made (Drawing credit S. Lowe).
A simplified picture of a Planck LFI receiver
The Planck
LFI receivers used thermal load as the reference since goal was to map extended CMB emission rather than
discrete sources as
in OCRA-p. Ideally the load would have been at the same
temperature as the CMBR (2.75K) to balance the receiver and hence maximise the
reduction in 1/f receiver gain fluctuations; the load was actually at 4K.
Nevertheless the knee frequency was reduced from ~100 Hz to ~40 mHz (t ~ 25 secs)
an improvement of 2500. Small non-modelled
imperfections in component performance
prevented a greater improvement. (Picture
credit http://planck.caltech.edu/lfi.html )